The detector architecture used high speed charge binning to combine signal from each sampling window into a single charge packet. This was then passed through a multiplication register (Electron Multiplying Charge Coupled Device) operating with a typical gain of 100X to a conventional charge detection circuit. The detector achieved a typical quantum efficiency of 80% and a total noise in darkness of < 0.5 electrons rms. Development of the detector was supported by ESA (European Space Agency).
The CCD was designed for possible use as the detector in a space based LIDAR instrument with a 667ns temporal sampling window to give 100m spatial resolution. Use with a 355nm laser required a high quantum efficiency at ultra-violet wavelengths necessitating a back-illuminated CCD structure. Optical spot size and alignment issues required a 120µm square image area and a number of novel device concepts to extract charge from this detector area with low crosstalk between successive atmospheric samples were considered in the design phase. It was concluded that conventional charge binning in a two-stage process was the lowest risk approach.
CRITICAL DEVICE PARAMETERS
The system requires a high Quantum efficiency of >70% at 355nm. This was met by a back-illuminated CCD with e2v’s standard (UV optimised) ion implantation and laser anneal back surface treatment, together with a customised anti-reflection coating. As the device is designed to detect UV wavelengths and has no demanding spatial resolution requirements the silicon thickness and resistivity are not critical for optical performance, and were chosen for optimum performance from the L3 gain register.
The required dark signal is less than 0.3 electrons per atmosphere sample in LIDAR mode. This low value influenced the choice of device architecture and led to concepts in which multiplication gain was applied to the signals as early as possible. This required the multiplication register to operate at a frequency of 1.5MHz to match the signal sampling rate. Architectures which stored the signals before multiplication at a lower clock rate were rejected. Even with the optimum architectures the predicted dark signal at +20°C was approximately 4 electrons per sample and this value was dominated by the contribution from the multiplication register. Techniques such as ‘Inverted Mode Operation’ or dither clocking are not applicable to multiplication registers as the magnitude of the clock-induced charge generated in the multiplication register is increased dramatically under these conditions. Only two strategies are therefore available to meet the requirement. Firstly the CCD needs to be cooled to a temperature in the range −10°C to −20°C (the required value was confirmed by experiment in the programme). Secondly the width of the multiplication register, and hence the dark current generation area, was reduced at the input end where signal levels are small and tapered out to a normal value towards the output end, to accommodate the increasing signal.
L3 Gain Register (Multiplication Register)
In order to achieve the required noise performance it was predicted that multiplication gains in the range from 50 to 200 would be required. This range is readily achieved with a similar gain register to that used on previous e2v technologies designs using typically 500 multiplication stages. Apart from the tapering of register width discussed previously the register is therefore of conventional design, similar to that used on the CCD87 for example.
The stability of the multiplication gain was reviewed as this depends on temperature and on the operating Voltages, being a very strong function of the amplitude of the high Voltage clock pulse (RØ2HV). Analysis of results from other devices suggested that a temperature stability of ±0.25°C and a Voltage stability of 4mV would be necessary to achieve the required gain stability. Part of the characterisation phase of the programme was to demonstrate that these levels were achievable.
Comparison with other devices also suggested that the required levels of linearity should be achievable with a standard register design for the system signal levels and the range of gains discussed above.
To allow calibration of the multiplication gain and measurement of linearity an electrical input structure at the start of the gain register was proposed, based on similar structures which had been used on test devices produced by e2v. Electrical input was preferred rather than optical methods as it allows better control and charge measurement for calibration.
It is known that for a fixed high voltage register clock amplitude, the on chip multiplication gain drops as the device is run . This process is known as ageing and depends on the total quantity of charge transferred through the multiplication register. In order to maximise the useful life of the sensor it is important to ensure that only the wanted signals are passed through the register. The low duty cycle of the system, 400 signal samples in 10ms, should then ensure a tolerable level of ageing over the mission lifetime.
Antiblooming and Dump Drains
Various drain structures are required in the device to accept unwanted or excess signals. Antiblooming drains cannot be included in the image section as a requirement to measure the brightness of the locally reflected ‘signal at laser emission’ was included in the specification. This signal is likely to exceed the capacity of the image section pixels but may still be measured if the bloomed signal in several pixels is added together. An antiblooming drain along the gain register (similar to other L3 CCDs) can be used to limit excess signals in the multiplication register, e.g. from specular echoes, and prevent such signals corrupting useful data or ageing the register excessively.
Dump drain structures, similar to those used on standard imaging CCDs, can be used to remove the ‘signal at laser emission’ if it is not to be measured.
Collection of Signal from 120µm Detector
Charge generated within the 120µm square detector area in a 667ns interval must be combined into a single CCD element at the input of the gain register. This process must minimise the crosstalk between successive temporal samples. Charge transfer across a single pixel of this dimension would be extremely slow, particularly at the very low signal levels (~ 1e-per sample) down to which the sensor was required to operate. A number of architectures to achieve the required performance were considered but it was concluded that the lowest risk was the use of conventional clocked binning of charge in an array of smaller pixels. This has the secondary advantage that the sensor area can be operated in a conventional imaging mode for alignment purposes etc. The number and size of the pixels into which the detector is divided was determined by the trade off between clock frequency and transfer efficiency. A larger number of smaller pixels requires a higher clock frequency to read out in the available time. A smaller number of larger pixels will have decreased transfer efficiency due to the slower charge transit time, which increases approximately as the cube of the pixel dimension. A 6 x 6 pixel array of 20μm square pixels was calculated to be optimum. This pixel size allows clocking at 24MHz with good transfer efficiency, which enables six image and two overscan pixels to be binned within a 667 ns sample period, with sufficient time remaining for the other clocking which is required.
For typical levels of charge transfer efficiency the crosstalk between successive temporal samples of the optical signal is dominated by the ‘frame shift smear’ in the image section. A model was developed to calculate this for a range of optical spot sizes and positions and confirmed that the specified value of 13% could be met
The architecture of the device is shown in Fig. 2 and described in the following sections.
The image section consists of a central 6 × 6 pixel array with additional rows and columns to minimise edge effects. Charge from the additional columns on each side is directly dumped to drains next to the binning register (not shown in the schematic). The image section has a total of 10 rows with the photosensitive region defined by a metal light shield, which is deposited directly on the CCD. Two-phase clock electrodes are used to simplify the high speed clocking required to perform charge binning. Charge from the whole image section is binned into a summing well (SW) adjacent to the binning register but isolated from it by a separately clocked transfer gate (TG).
The binning register receives signal charge from the image section and is clocked to bin a row of charge into the first element of the gain register. The binning register has a four-phase electrode structure incorporating the barrier implants used for two-phase electrodes. This allows bi-directional charge transfer with simple two-phase clock waveforms by appropriately pairing electrodes. Charge transfer in the reverse direction (without binning) is used when the device is operated in a simple imaging mode. A gated dump drain along the side of the binning register allows any unwanted signals to be dumped directly without transfer through the multiplication register.
The multiplication register is typical of that used in other e2v L3 CCDs except for the reduced width at the input end, as discussed above. It consists of 520 multiplication stages with additional non-multiplying stages at both ends, as is standard. An antiblooming drain runs the full length of the register to remove excess charge from any very bright signals.
The device includes two independent output circuits of nominally identical performance. Output 1, the gain register output, is used in LIDAR mode while output 2 at the other end of the binning register is used in imaging mode e.g. for alignment or for measurement of the bright locally reflected ‘signal at laser emission’. The two outputs have a nominal responsivity of 3μV per electron, are capable of operation at 1.5MHz clock rate and have a read noise of 10 electrons rms. at this rate.
Charge Injection Structure
The charge injection structure consists of an input diode and a separate control gate. It is typically used in conjunction with a precision current source to inject a known quantity of charge into the gain register on each clock cycle. The multiplication gain is then measured directly as the ratio between the signal current at the output of the gain register (reset drain current) and the input current. The charge injection circuit may be turned off completely when not required by applying a suitable positive bias (+20V typical) to the input diode.
The electro-optic performance of a number of back-illuminated devices was assessed at e2v technologies using an engineering test camera with a specially built light source, which produced a simulated LIDAR echo signal. The source used two LEDs and a laser diode which could be independently pulsed with a range of currents under control of the CCD clock sequencer to give a wide range of signal levels and patterns.
The high Voltage clock pulse amplitudes required to give gains of 50 and 200X at -20°C and a gain of 100X at −20°C, −15°C and −10°C were measured. These operating conditions were used in subsequent tests to determine the recommended operating point, which was part of the objective of the characterisation. All devices were very similar requiring typically 40V for 100X gain at −20°C, which was the final recommended condition.
The stability of the multiplication gain was measured as the peak to peak range of the mean signal level of each set of 400 signal samples (equivalent to the echo from a single laser pulse) over a 15 second period in LIDAR mode with constant illumination from one of the LED light sources. The measured value of ±0.8% exceeds the specification of 1%. However a review of the measurement established that the variation in mean level of the 400 samples was dominated by the random noise component due to photon shot noise and the excess noise factor (see section D. below). Calculation of the average signal over successive sets of 4 x 400 samples gave a gain stability within specification. This demonstrated that the required levels of Voltage and temperature stability are achievable.
The quantum efficiencies (QE) of two typical devices at 355nm were 81.8% and 81.6% which met the specification of >70% with some margin. However it was observed that another device sample showed some instability of quantum efficiency over time and an investigation was carried out.
It was concluded that the most likely explanation of the changes seen is that volatile contamination is condensing on the CCD when it is cooled.
Total Noise in Darkness
The total noise in darkness, which includes the contribution of dark current shot noise, was measured for the same set of operating conditions as the multiplication gain. Typical values were 0.43e-rms per sample. for 100X gain at −20°C with significantly higher values for lower gain or higher temperature and only a slight decrease at 200X gain and −20°C.
The contribution of readout noise to the total was approximately 0.15 e- rms as the effective contribution from the amplifier and system (15e-) is reduced by the gain of the multiplication register.
Excess Noise Factor
When multiplication gain is employed, there is an additional contribution to the noise due to the stochastic nature of the charge multiplication process. The excess noise factor, F, is defined as the input referred noise with gain divided by the input referred noise without gain, under conditions of zero readout noise. If in the multiplication process each signal electron is assumed to behave independently of all the other signal electrons, it can be shown that, for large multiplication gain .
where α is the probability of multiplication gain per stage. Since the CCDs have 520 multiplication gain stages, a ≪1, and this gives F = √2.
The excess noise factor from the multiplication process was measured for a range of signal levels with a gain of 100 and was close to the theoretically expected value of √2 for small signals. However for input signal levels above approximately 400e- the value decreased. To investigate this effect measurements of the excess noise factor were made for different multiplication gains and it was observed that the input signal level up to which the full excess noise was seen decreased with increasing gain. The break point corresponded approximately to a constant output signal level. It was therefore suspected that the effect was due to signal charge coming into contact with traps at the silicon surface. Such trapping and subsequent release of charge would be expected to have a smoothing effect on the excess noise. Trapping would also give rise to charge transfer inefficiency (CTI) and so measurements of this were made for a range of gains and signal levels. Typical results are given in Fig 3 which shows the residual signal in successive dark samples following a block of 400 illuminated samples in LIDAR mode at a range of signal levels. It is clear that the trap release time constant becomes longer at larger signal levels. Charge interaction with these slow traps would have a more significant smoothing effect on the excess noise.
The dark signal in LIDAR mode cannot be measured directly but was estimated from the Total Noise in Darkness, the readout noise and the excess noise factor. The estimated dark signal was less than 0.1 electrons per sample at −20°C with 100X gain, which meets the specification of <0.3 electrons.
The crosstalk performance of < 1.7% which was measured at a signal level of 500e- per sample is well within specification of <13%. This value is achieved with a 20µm diameter light spot positioned centrally in the image section and with a 667ns optical pulse starting and finishing at approximately the middle of a ‘frame transfer’ As the spot is moved vertically either the leading or trailing crosstalk increases, in line with the predictions of the model.
Under the recommended operating condition a linearity error of <1% was maintained for input signal levels up to 1300e− at x100 gain which covers the specified range of atmosphere sample signals. The ‘normal ground echo’ signal defined as 1900e− was handled with a linearity error of no more than 4%.
Some additional linearity measurements were also performed to investigate linearity down to very low signal levels. The use of the charge injection circuit is restricted to moderate signal levels by the presence of leakage currents.
An alternative measurement based on optical inputs was therefore devised. The results of this measurement are shown in Fig 4, which confirms that good linearity performance is maintained down to very small input signals.
Lidar Mode Demonstration
The performance of the CCD in LIDAR mode was demonstrated using various signals generated by the pulsed optical source to simulate atmospheric, local and ground echoes. An example is shown in Fig 5.
This shows 256 successive acquisitions during each of which the signal level from the LEDs was increased in a series of steps, acquiring 50 samples at each signal level, followed by a short pulse (20ns duration) from the laser diode to simulate the ground echo.
This development has demonstrated the potential for L3VisionTM technology to deliver sub-electron levels of total noise in darkness together with adequate gain stability to allow its use in measuring instruments to be considered. Other electro-optic properties typical of standard CCDs can be maintained.