## 1.

## Introduction

With the explosive development of Internet and personal data services in the past decade, our demand for network bandwidth is rapidly growing. To improve the capacity of fiber links and networks, many critical techniques such as wavelength division multiplexing, polarization multiplexing, and multilevel modulation have been applied, but the capacity of single mode fiber is still limited by fiber nonlinearities and amplifier noise. After time, wavelength, phase, and polarization, space is the next degree that can be multiplexed to further promote the capacity of optical fiber systems. Mode division multiplexing (MDM) in the few mode fiber (FMF) is a practical way to improve the capacity and solve the bandwidth crisis.

MDM systems based on FMFs have been theoretically studied, and some experiments have been demonstrated.^{1}^{,}^{2} Mode coupling and differential mode delay are two major challenges to the practicability of this promising technology. In an MDM system, orthogonal spatial modes are used to transmit signals as independent channels. However, along a practical fiber link, the imperfect parameters always exist, including micro bending, fiber twisting, and fluctuant refractive index distribution. All these factors damage the orthogonality of spatial modes and lead to random mode coupling. In addition, mode coupling may also occur at the multiplexer and demultiplexer. The other major factor that limits the capacity is differential mode delay. The values of modal delay mainly depend on fiber geometric dimensioning and refractive index distribution. Large model dispersion can suppress mode couplings, but when the two factors work together, signals carried by the modes get distorted. Compared with MMFs, the FMFs contain fewer modes and have slighter intermodal impacts, but a multiple-input multiple-output (MIMO) equalizer is still needed after mode demultiplexer for signal recovery.

Least mean square (LMS) and constant modulus algorithm (CMA) are conventional adaptive equalization algorithms which have been used in the MDM systems.^{3}^{,}^{4} The training sequence used in LMS enlarges the system overhead, while regular CMA needs to choose a suitable learning step. The equalizer converges slowly with small steps and cannot converge with large steps for accurate estimation. Recursive least squares (RLS) have faster converge speed than LMS,^{5} so an RLS-based CMA algorithm will have a better performance than regular CMA. It has been reported to be adopted in wireless adaptive arrays^{6} and coherent optical systems.^{7}

In this paper, first the transmission model of a MDM system under weak coupling regime and the algorithm of MIMO recursive least squares constant modulus algorithm (RLSCMA) are discussed in Sec. 2, then a $6\times 6$ MDM system with a MIMO signal processing using RLSCMA is simulated in Sec. 3.

## 2.

## Theory and Algorithm

## 2.1.

### Few Mode Fiber Channel Analysis

In an FMF, the spatial mode travels in a complicated way, and many efforts have been made to analyze and model it. The two major factors, random mode coupling and mode delay have binding effects. Generally speaking, a large coupling would lead to small mode delay. In our discussion, the FMF works under a weak coupling regime,^{8} and the modal delays grow linearly with the length of the fiber link.

To discuss the channels for modes in an FMF, we can compute its transmission matrix. Mode coupling occurs along the fiber link randomly, so we have to model it in a discrete way. The fiber link can be divided into multiple segments; within each segment, signals are assumed to travel independently and mode coupling occurs at the joints of the segments.

Defining total transmission matrix of fiber link as $T(\omega )$, the model of the MDM system can be described as

where $\mathbf{X}={({\mathbf{x}}_{1},{\mathbf{x}}_{2},\cdots ,{\mathbf{x}}_{N})}^{\mathrm{T}}$ and $\mathbf{Y}={({\mathbf{y}}_{1},{\mathbf{y}}_{2},\cdots ,{\mathbf{y}}_{N})}^{\mathrm{T}}$ are input and output signals, respectively.The transmission matrix of the segment $k$ can be expressed as

where ${M}_{k}$ is a linear propagation matrix, describing modal delay, chromatic dispersion (CD), and span loss that the modes suffer from in this segment, and ${C}_{k}$ denotes the mode coupling matrix at the junction between this and the next segment.For a system with $N$ operating spatial modes, ${M}_{k}$ can be expressed as

## (3)

$${M}_{k}(\omega )=\left(\begin{array}{ccc}{\mathrm{e}}^{{g}_{1}-j\omega {\tau}_{1}-j{\omega}^{2}\frac{{D}_{1}{\lambda}^{2}}{2\pi c}{L}_{k}}& \cdots & 0\\ \vdots & \ddots & \vdots \\ 0& \cdots & {\mathrm{e}}^{{g}_{N}-j\omega {\tau}_{N}-j{\omega}^{2}\frac{{D}_{N}{\lambda}^{2}}{2\pi c}{L}_{k}}\end{array}\right),$$Thus, the total transmission matrix of the fiber link is

The polarization-multiplexed transmission is usually applied in each spatial mode. Thus, the influence of polarization mode dispersion (PMD) must be considered and involved in the model. The Jones Matrix is applied to the model polarization mode channel in each spatial mode. For each spatial mode, the channel can be described as

## (5)

$${H}_{p}=\left[\begin{array}{cc}\mathrm{cos}\text{\hspace{0.17em}}\theta & -\mathrm{sin}\text{\hspace{0.17em}}\theta \\ \mathrm{sin}\text{\hspace{0.17em}}\theta & \mathrm{cos}\text{\hspace{0.17em}}\theta \end{array}\right]\left[\begin{array}{cc}{e}^{j\omega {\tau}_{p}/2}& 0\\ 0& {e}^{-j\omega {\tau}_{p}/2}\end{array}\right]\left[\begin{array}{cc}\mathrm{cos}\text{\hspace{0.17em}}\theta & \mathrm{sin}\text{\hspace{0.17em}}\theta \\ -\mathrm{sin}\text{\hspace{0.17em}}\theta & \mathrm{cos}\text{\hspace{0.17em}}\theta \end{array}\right],$$Therefore, the transmission channel of an $N$-mode system can be described by a $2N\times 2N$ matrix shown as Eq. (5), thus, a $2N\times 2N$ MIMO digital signal processing (DSP) equalizer is needed

## (6)

$$H=\left(\begin{array}{ccc}{H}_{\mathrm{1,1}}& \dots & {H}_{\mathrm{1,2}\text{\hspace{0.17em}}\text{\hspace{0.17em}}N}\\ \vdots & \ddots & \vdots \\ {H}_{2\text{\hspace{0.17em}}\text{\hspace{0.17em}}N,1}& \cdots & {H}_{2\text{\hspace{0.17em}}\text{\hspace{0.17em}}N,2\text{\hspace{0.17em}}\text{\hspace{0.17em}}N}\end{array}\right).$$## 2.2.

### Recursive Least Squares Constant Modulus Algorithm

A regular CMA algorithm has a cost function as follows:

To apply recursive least-square method, the cost function should have a quadratic relationship with the equalizer weight vector $\mathbf{w}(n)$. Introduce the forgotten factor $\lambda $ ($\lambda <1$), set $p$, $q=2$, then rewrite ${J}_{p,q}$ into the form of a weighted time average sum as

where $\mathbf{u}(k)=\mathbf{y}(k){\mathbf{y}}^{H}(k)\mathbf{w}(k-1)$ and $\mathbf{y}$ denote the input vector of the equalizer.The algorithm can be shown as follows:

I Initialization: $\mathbf{w}(0)={[\mathrm{1,0},\cdots 0]}_{1\times L}$, $\mathbf{P}(0)=\mathrm{\Phi}{(0)}^{-1}={\delta}^{-1}{I}_{L\times L}$

($L$ denotes length of $\mathbf{w}$, $\mathrm{\Phi}$ is input autocorrelation matrix, $\delta $ is defined as regularization factor)

II for $k=1,\cdots ,n$, compute and update following variables

III Update tap vector: $\mathbf{w}(k)=\mathbf{w}(k-1)+\mathbf{g}(k){e}^{*}(k)$,

Return to II and iterate till convergence.

These are the basic steps of RLSCMA, and can be extended for MIMO equalization. The variable $\delta $ is the norm of the input autocorrelation matrix, which is usually set as a small number when the channel status is good, and a large number with a bad channel status.

For an $N$-mode transmission system, the matrix $\mathbf{P}$ in the algorithm above should have a dimension of $2NL\times 2NL$. For the $i$’th receiver, ${\mathbf{w}}_{i}=[{\mathbf{w}}_{i,1}^{\mathrm{T}},{\mathbf{w}}_{i,2}^{\mathrm{T}},\cdots ,{\mathbf{w}}_{i,2N}^{\mathrm{T}}]$ are a set of $2N$ equalizers and the equalized signal can be obtained by

where ${\mathbf{w}}_{i}$ can be obtained by the RLSCMA algorithm.## 3.

## Simulation and Results

A $6\times 6$ MIMO transmission system with three spatial modes (LP01 and degenerate LP11 modes) shown in Fig. 1 is simulated, where each mode carries a 20-Gbps DP-NRZ-QPSK signal. All six signals are coherently detected and sent to the signal processing unit.

In the simulation, the channel model consists of two parts; the channel of the multispatial mode and the channels of the polarization modes within each spatial mode are separately considered. The matrix model discussed in Sec. 2 is applied to describe the spatial mode channel, and the mode coupling matrix is approximately computed with two major vectors induced by fiber twisting, $\eta $ and $\phi $, where $\eta $ is the ratio of the random splice offset and field radius of the LP01 mode, and $\phi $ is the random rotated angle between sections.^{9}

The simulation parameters are set as follows: transmission length $L=50\text{\hspace{0.17em}}\text{\hspace{0.17em}}\mathrm{km}$, operating wavelength ${\lambda}_{c}=1550\text{\hspace{0.17em}}\text{\hspace{0.17em}}\mathrm{nm}$, $D=17\text{\hspace{0.17em}}\text{\hspace{0.17em}}\mathrm{ps}/\mathrm{nm}/\mathrm{km}$, differential mode delay between LP01 and LP11 modes $\mathrm{DMD}=60\text{\hspace{0.17em}}\text{\hspace{0.17em}}\mathrm{ps}/\mathrm{km}$, $\phi =0\sim \pi /8$, $\eta =\phantom{\rule{0ex}{0ex}}0\sim 0.1$, $\theta =\pi /6$, polarization mode delay ${\tau}_{p}=0.3\text{\hspace{0.17em}}\text{\hspace{0.17em}}\mathrm{ps}/\mathrm{km}$. The large effective area of FMF can suppress nonlinear effects. To simplify the analysis, nonlinear affects and mode dependent loss are ignored.

Figure 2 shows the architecture of the MIMO DSP used in this paper, where ${y}_{1}\sim {y}_{6}$ are the signals detected at the receiver, and ${z}_{1}\sim {z}_{6}$ are the outputs of the equalizer. First a group of six FIR filters is used to compensate the CD of each mode,^{10} then a $6\times 6$ MIMO equalizer array consisting of 36 FIR filters operating under the RLSCMA algorithm is applied to compensate mode coupling, modal dispersion, and PMD. The number of MIMO equalizer taps is decided by the differential mode delay in the full span and symbol rate,^{3} where $L=\lceil ({\tau}_{N}-{\tau}_{1}){r}_{os}{R}_{s}\rceil $ comes into 15 in this paper.

Figure 3 shows the simulated spatial mode patterns at the input and output of the FMF, where all the orthogonal modes are affected by mode coupling. It can be seen that the degenerate LP11 modes couple with each other more severely due to spatial twists of the fiber.

The eye diagrams of LP01-x and LP11a-x before and after equalization are compared in Figs. 4 and 5. As is depicted in the figures, the signals carried by the LP11 modes experience more severe damage than the LP01 mode, and the eye completely closes. After equalization, we achieve open eye patterns with both LP01 and LP11 modes. Because the mode pattern area of the LP01 mode is distributed in the center of the core and is larger than the LP11 modes, it suffers less influence from mode coupling induced by spatial mismatching and rotation in the applied model.

The constellations of the signal carried by LP11a-x mode before and after MIMO equalization are shown in Fig. 6. It can be seen from the constellations that the signal received is still badly distorted due to mode coupling and mode delay after CD compensation, however, these affects can be well compensated by MIMO equalizers.

We have also compared the RLSCMA performance with the traditional stochastic gradient descent CMA (SGDCMA). The bit error ratio (BER) curves of the two algorithms are illustrated in Fig. 7(a), where the LP11a-x mode is adopted for analysis. It can be seen that both algorithms realize an effective equalization for the received signal. Compared with SGDCMA, the required optical signal-to-noise ratio (OSNR) at BER of ${10}^{-3}$ is improved by 0.5 dB with the proposed RLSCMA. Figure 7(b) shows that the RLSCMA algorithm converges more rapidly than SGDCMA (with the same equalization effect), suggesting that it is more adaptive for the complicated FMF channel.

At the receiver, the signal BERs of the three modes carried on the $x$ and $y$ polarizations are calculated respectively, which are shown in Fig. 8. It can be seen that the signals on both $x$ and $y$ polarizations show similar performances after transmission. Before MIMO equalization, the received signals of the three modes suffer severe bit errors (shown by solid curves). Figure 8 also shows that the signals of the double LP11 modes have much higher BERs than that of the LP01 mode signal, which can be predicted from the eye diagrams in Figs. 4 and 5. After MIMO equalization, the BERs of all the modes are significantly decreased. The BERs below ${10}^{-3}$ can be achieved for all the simulated modes with the OSNR above 18 dB. The simulation results show that MIMO RLSCMA is qualified for mode demultiplexing interference cancellation.

We also simulate the transmission of MDM with 16-QAM signals and do MIMO equalization with RLSCMA. The constellations before and after equalization are shown in Fig. 9, where we can see the RLSCMA performs well with 16-QAM signals.

## 4.

## Conclusion

In this paper, an MIMO RLSCMA algorithm is proposed and applied to a $6\times 6$ MDM system for signal processing. The signals on all modes are successfully recovered in the simulation, verifying that the proposed algorithm can efficiently overcome the effects of mode coupling and differential mode delay a with fast converging speed.

## Acknowledgments

The financial supports from the National NSFC (No. 61425022/61275074/613070864/61475024), National High Technology 863 Program of China (No. 2013AA013403, 2015AA015501/02), NITC (No. 2012DFG12110), and Beijing Nova Program (No. Z141101001814048) are gratefully acknowledged. The project is also supported by the Universities PhD Special Research Funds (No. 20120005110003/20120005120007) and Fund of State Key Laboratory of IPOC (BUPT).

## References

## Biography

**Xiaolong Pan** is an undergraduate student at Beijing University of Posts and Telecommunications (BUPT) and a member of the State Key Laboratory of Information Photonics and Optical Communications in BUPT. His research interests focus on optical communications and optical signal processing.

**Bo Liu** is an assistant professor at BUPT and a member of the State Key Laboratory of Information Photonics and Optical Communications in BUPT. His research interests include broadband optical communications and optical signal processing.